Electronic circuit producing pulse sequences of different rates



' Dec. 6, 1966 R. A. RODNER ELECTRONIC CIRCUIT PRODUCING PULSE SEQUENCES OF DIFFERENT RATES 5 Sheets-Sheet 1 Filed Sept. 27, 1965 K 0 0 T w m. I 7 c m a w a a m @4 @016 A M a A E T A 5 W fa 5 E v I7; "C1 3 .T'T u l U 8 (5 KS 6 V VFW T .VII'F/ i 6 H 4 m 6 W Z a w. 2 L

INVENTOR. AOfiE/Fl' 4. KOflNL-K BY W M Alia/way Dec. 6, 1966 3,290,606

R. A. RODNER ELECTRONIC CIRCUIT PRODUCING PULSE SEQUENCES OF DIFFERENT RATES Filed Sept. 27, 1965 5 Sheets-Sheet 2 Dec. 6, 1966 RODNER 3,290,606

ELECTRONIC CIRCUIT PRODUCING PULSE SEQUENCES OF DIFFERENT RATES Filed Sept. 27, 1963 5 Sheets-Sheet 3 United States Patent 3,290,606 ELECTRONIC CIRCUIT PRODUCING PULSE SEQUENCES OF DIFFERENT RATES Robert A. Rodner, Lake Park, Fla., assignor to Radio Corporation of America, a corporation of Delaware Fiied Sept. 27, 1963, Ser. No. 312,099 8 Claims. (Cl. 32862) This invention relates to pulse generating systems, and more particularly to improved systems for generating sequences of pulses.

In many electronic systems, the operation of various units is controlled by sequences of timing or clock pulses provided by a special pulse generator. These timing pulses are used, for example, to insure that the various units are properly synchronized and operate at preselected times. It is conventional to design the logic and gating circuits of the various units so as to operate at a predetermined frequency or repetition rate. The sytsem timing pulse rate then is maintained at this predetermined rate by using a high precision oscillator circuit such as a crystal controlled oscillator. A desired pulse sequence according to one arrangement is generated by coupling logic circuits and delay lines in suitable fashion to the oscillator to provide desired pulses at specified times. Another arrangement for generating pulse sequences is to use the oscillator pulses to drive a shifting type register or ring counter with the various stages providing the desired pulses of the sequence.

In such arrangements, however, the repetition rate of the pulses of the sequence is fixed by the response time of the logic circuits or the shifting register. For example, a shifting register using circuits designed for a 500 kilocycle frequency is not suitable for providing a one megacycle repetition rate pulse sequence, and so on.

It is often desirable to have a pulse generator which is capable of operating at different repetition rates, particularly rates higher than the predetermined rate of the individual logic circuits used in the generator.

Also, certain systems require different length pulse sequences for different system operations. One method of generating these variable pulse sequences, for example, is to provide a separate generator for each different sequence and to selectively activate the generator corresponding to the desired sequence. In general, such variable sequence clock pulse generators require a relatively complex interconnection of the circuits and are relatively expensive.

It is an object of the present invention to provide an improved pulse generator capable of producing pulse sequences at different repetition rates.

Another object of the present invention is to provide an improved pulse generator capable of producing variable pulse sequences.

A timing pulse generator in accordance with the present invention includes two shifting registers. The stages in each register are connected to each other in ordered fashion. The output of the lowest order stage of one register also is applied as an input to the lowest order stage of the second register. Signals inserted in the registers are shifted in response to signals from anoscillator. Oscillator pulses of one phase are coupled to shift inputs of the first register while the other phase oscillator pulses are coupled to shift inputs of the second register. A set of decoding gates each having inputs connected to certain stages of both registers provide the sequence of timing pulses in response to the signals inserted in the regis- An important feature of the invention is the production of timing pulses which have a repetition rate (or frequency) which is a multiple or a sub-multiple of the oscillator frequency. For example, by using two-input decoding gates, the timing pulses may have a repetition rate which is a multiple or a sub-multiple of the oscillator frequency. By using three-input decoding gates, the timing pulses may have still another different repetition rate than the oscillator frequency.

Another feature of the invention is that the generator may be easily arranged to produce either single or recurrent sequences of particular timing pulses, as desired.

In the drawing:

FIGURE 1 is a schematic diagram of an arrangement of registers in accordance with the invention;

FIGURE 2 is a schematic diagram of one decoder unit useful with the registers of FIGURE 1;

FIGURES 3a, 3b and 30, all to the same scale, are timing diagrams useful in explaining the operation of the timing pulse generator;

FIGURE 4 is a schematic diagram of another decoder unit useful with the registers of FIGURE 2; and

FIGURE 5 is a schematic diagram of a register stage suitable for use in the circuit of FIGURE 1.

The pulse generator of FIGURE 1 includes first and second registers 10 and 12. In the illustrative embodiment, each of the registers is provided with three stages by way of example. Registers with more or less than three stages can be used as necessary or desired. A large number of stages would provide more pulses per sequence whereas fewer stages would provide fewer pulses per sequence. The three stage C0, C2 and C4 of register 10 are connected in cascade by connecting the respective outputs of lower order stages to respective inputs of the higher order stages. The register 12 has stages C1, C3 and C5 similarly connected in cascade. The outputs of the stage C6 of the first register 16 are also connected to the respective inputs of the first stage C1 of the second register 12.

Each register stage comprises a triggerable flip-flop having set and reset inputs and corresponding outputs. For convenience, the output of the flip-flop corresponding to the set state is designated by the flip-flop number, i.e., C0, and the output corresponding to the reset state is labeled with the flip-flop number with a bar over it, i.e., C3 The two outputs of the flip-flop, for example C0 and Gil, are complementary, that is, when one is at a high level the other is at a low level, and vice versa. Each of the flip-flops is arranged so that when it is in the set condition, the unbarred output is relatively loW and when it is in the reset condition, the barred output is relatively low. Each of the flip-flops also has a trigger or shift input (T), A register flip-flop is placed in the set or reset condition by first applying a relatively high level to an appropriate one of the inputs and then applying a relatively high level trigger pulse to the trigger input T. The register flip-flops also may be reset directly by a common reset input not shown in FIGURE 1. Details of a suitable flip-flop circuit for use in the generator of FIGURE 1 are discussed later in connection with FIG- URE 5.

The set and reset inputs of the C0 flip-flop of the register 10 are connected, respectively, to the Run and Run outputs (the complementary outputs) of a Run flipflop 14. The Run flip-flop 14 is reset by the output of a gate 16. The gate 16 and each of the other gates described herein may be transistor type logic gates each performing the NAND (not and) logic function. The set input of the Run flip-flop 14 is controlled by the output signal of a start gate 18 and a stop gate 20. The stop gate 20 is connected by Way of a single-pole, single-throw stop switch 22 to the set input of the flip-flop 14. The start gate 18 has one input connected by way of an inverter 22 (which may be a single input NAND gate) and one terminal of a single-pole, double-throw switch Initially, the register stages and the Run flip-flop are all in the reset condition and all the barred outputs are at a relatively low level. When the start switch 24 (FIGURE 1) is momentarily thrown to the on terminal,

24 to a source 26 of bias voltage. An inverter is indicated 5 the inverter 22 applies a relatively low enabling level to in the drawing by a circle. The second or off terminal start gate 18. The coincidence of this enabling level with of the switch 24 is connected to circuit ground. The a negative going phase B pulse activates the start gate switch 24 is indicated as a mechanical switch, however, 18 to apply a high level pulse to the set input of Run in practice an electronic switch can be used. For exfiip-fiop 14 causing its Run output to be high." The ample, the switch 24 and inverter 22 can be replaced high Run output enables the set input of the C0 stage. by a single NAND gate with a start pulse applied to its The start switch 24 can then be returned to its 011 base input. position after the Run flip-flop is set. Lines a, b, c and d Oscillator 30 pulses of one phase labeled B in the of the FIGURE 3a timing diagram indicate this start drawing are applied to the second input of the start gate sequence. In the case of an electronic start switch, a 18. The oscillator 30 may be a free-running, squarestart pulse is applied from any suitable source to enable wave oscillator which is crystal controlled. The phase the start gate 18. The flip-flop states at this time are B pulses, when of positive polarity, prevent the signal indicated in line 1) of the table. The next phase B from nverter 22 from activating start gate 22. The phase pulse sets the C0 stage causing its '66 Output to go high B Osclnatof P l also are pp to h trigger Inputs thereby enabling the set inputs of the C1 and C2 stages. of the feglshef 10 stages- The osfllllatof 30 Pulses The states of the flip-flops at this time are indicated in are coupled by "Water 32 9 the mggel' mputs (T) line (2) of the table. At this time the first decoder gate of the fa e 12 Stages; The Invert? 32 Outputs labeled G0 (FIGURE 2 is activated initiating the first timing 3? Q i: gi gigi ggz 180 out of phase wlth pulse CPO since both the C0 and Ci inputs are low.

56min outputs of r re ism Sta es re As indicated in line 3 of the table, the next phase I; p g g a A oscillator pulse sets the C1 flip-flop causing its C1 outp .ed to the inputs of a decoder 34. One arrangement of put to be low, thereby enabling the second decoder gate a decoder 34 is shown in FIGURE 2. This particular decoder is arran ed to Su 1 an out ut ulse Se uence G1 and enabling the set input of the register stage C3.

g pp y P q At this time the first timing pulse CPO is terminated and at twice the repetition rate of the oscillator 30. A set th e second timing pulse CPI is initiated due to the presof nine two-input gates G0-G8 receives the outputs of the register flip-flops. The gate G0 receives the C0 and i t f slgnals a g p ase pu se se s e ipop causing i s ou pu C1 Slgnals gate G1 recewes the c2 i to be low. The C0 flip-flop remains set because of the and so on, with each of the gates receiving a different 1 ow Run output from the Run flip-flop. At this time the palr of slgnals one from a siage of reglster 10 and the 3:" second timing pulse CPI is terminated and the third 0 d other R l f reglstzr g i l timing pulse CP2 is initiated due to the presence of the rece ves t e un signa rom t e um ipop 1 11 low level C2 and 53 Signals. additional input from a command line S8 may, for reasons Th t h A 1 h C3 fi h discussed later be cou led to all the decoder ates. e Hex p ase Pu Se sets t P causmg t e p g C3 out ut to be low Th C1 fl -fi t due to However the line S8 is not necessary for the operation p 6 1p Op remams Se 40 the presence of the low level 1 input from the C0 flipof the decoder and can be omitted.

The ates of decoder 34 rovide a Se Hence of ositive flop. The states of the various flip-flops at this time are clock has assumeg how; that indicated in line 5 of the table. At this time the third p y p s timing pulse CP2 is terminated and the fourth timing pulse the pulse generator is to be used in providing timing CPS d d h I l 1C3 d l pulses for a system employing NAND logic gates. Hence, AI lslmltRlate g e an C4 slgna a set of inverters 1048 is used to invert the positivei qutput of g rfset going outputs of the gates G0G8 to produce a sequence ga e W 1c 18 e at 0t Inputs by t 6 9 f 1dr-t lock luses' level C2 and C3 signals. The C0 flip-flop now has a high 0 mega We going p0 P level a lied to its reset n ut The act'on f th R The operation of the timing pulse generator will be fi t d f f'FIGUREg e explained in connection with the following table and Op1s,m at me O the timing diagram of FIGURE 3a. Successive rows of of feglster filp'flops C0435 1S mdlcated at lmes the Table, below, correspond to the conditions of the respectively Q FIGURE flip-flops during successive A and B phases of the oscillator The fOHOVYIPg Phase B Pulse Changes the C0 pulses. The 1 and O in the A and B columns indicate a reset cofldltlon and Sets the P' P' h C2 positive polarity pulses of the A and B phases. A 1 QP l'emalhs Set due the enahhhg level PPh in one of the c0 c5 and R columns indicates that the thls p a e pulse y e C0 hpp- At thls tune the flip-flop designated by that column is in the set condition fourth tlmlhg Pulse CP3 1S telmlhated and the fifth timing during the particular A or B oscillator pulse. A O in a pulse CP4 is initiated due to the presence of the low level column indicates the designated flip-flop is reset during C1 and C4 inputs to the gate G4. The states of the flipthe particular oscillator pulse. flops at this time are indicated in line (6) of the table.

Table Phase Phase C0 C1 C2 C3 C4 C5 Run Timing A B 1 Pulse 1 0 0 0 0 0 0 0 i 0 1 1 0 0 0 0 0 i CPO. l 0 1 i 0 0 0 0 i 0P1. 0 1 1 i 1 0 0 0 i CP2. 1 0 1 i 1 1 0 0 0 0P3. 0 i 0 i i 1 1 0 0 0P4. 1 0 0 0 1 1 i i 0 0P5. 0 1 0 0 0 i 1 1 0 CPS. 1 0 0 0 0 0 1 1 i 0P7. 0 i i 0 0 0 0 i 1 Stop or CPO. 1 0 1 1 0 0 0 0 i 0P1.

The following phase A pulse changes the C1 flip-flop to the reset condition because of the enabling level from the reset C flip-flop and sets the C flip-flop due to the enabling level from the set C3 flip-flop. At this time the fifth timing pulse CP4 is terminated and the sixth timing pulse CPS is initiated due to the low CT and C2 inputs to gate G5.

The following phase B pulse changes the C2 flip-flop to the reset state due to the enabling level from the reset C0 flip-flop. At this time the sixth timing pulse CPS is terminated and the seventh timing pulse CP6 is initiated due to the low level 137 and C3 inputs to the gate G6.

The following phase A pulse changes the C3 flip-flop from the set to the reset condition due to the enabling level output from the reset C1 flip-flop. The flip-flop states at this time are indicated in line (9) of the table. At this time the seventh timing pulse CP6 is terminated and the eighth timing pulse CP7 is initiated due to the presence of the low level C? and C4 inputs applied to the gate G7.

The and C4 inputs are also applied to the stop gate 20 and when the stop switch is in the closed position, the Run flip-flop is changed from the reset to the set condition during the phase A pulse as indicated at line k of FIGURE 3a. If the stop switch 22 is open (as shown), the Run flip-flop remains reset. In such case, line (9) of the table would indicate a 0 in the Run flip-flop column.

Assuming the stop switch 22 to be open, the Run flipflop remains reset and the RE level is low. Hence, the gate G8 now is activated due to the low level inputs and the final pulse of the sequence corresponding to a stop condition is initiated. The following phase A pulse changes the C5 flip-flop from the set to the reset condition clue to the high level 0 output from the C3 flipfiop. At this time the C5 input to the decoder gate G8 is high terminating the stop pulse. Thus, at this point in the operation each of the register stages C0-C5 have been returned to the initial reset condition.

If it is desired to continuously generate the sequences of timing pulses, then the stop switch 22 is placed in the closed position. The C3, C4 signals then change the Run flip-flop to the set condition as indicated in line (9) of the table. The next phase B pulse then changes the C0 flipflop to the set condition and the C4 flip-flop to the reset condition. At this time the eighth timing pulse CP7 is terminated and the m and C5 inputs to the decoder gate G8 are both high. However, at this time the Run flipflop is in the set condition due to the closing of the stop switch 22, hence the it uh level is high and the gate G8 is not activated.

Thus. after the eighth timing pulse CP7, a new timing pulse CPO is generated due to the presence of the C0 and U1 high inputs as indicated in line (10) of the table. The second and subsequent sequences of timing pulses are then generated as described above until the stop switch 20 is changed to the open position.

The timing diagram of FIGURE 3b indicates the relationship of the sequence of clock pulses generated by decoder 34 with respect to the control signals of FIGURE 4.

FIGURE 4 is a schematic diagram of another embodiment of a decoder 34' arranged to provide timing pulse sequences having a repetition rate two-thirds that of the ocsillator frequency. The decoder includes, for example, three two-input NAND gates GlO-G12. The first gate G10 receives inputs C1 and U3, the second gate G11 receives the inputs C2 and C3 and the third gate G12 receives the inputs U2 and (1 5. An additional command line 82/ 3 may be coupled to each of the decoder gates as an enabling input. However, the command line 52/ 3 also is not necessary for the operation of the decoder 34 and can be omitted.

The operation of a system using a decoder 34' is similar to that described in connection with the decoder of FIGURE 2. Referring to the above table, for example,

6 it is seen that the timing pulse from gate G10 of the de coder is initiated when the stage C1 is set and this timing pulse continues for three half cycles of the oscillator until the stage C3 is set. The second timing pulse C21 from gate G11 is initiated when the stage C3 is set and continues for three half cycles of the oscillator until the stage C2 is set. The third time pulse CP2 from gate G12 is initiated when the stage C2 is reset and continues for three half cycles of the oscillator when the stage C5 is set. Thus, the decoder of FIGURE 4 produces one timing pulse for each three half cycles of the oscillator. The timing diagram of FIGURE 3c indicates the relation between the decoder 34 output pulses and the signals from the register stages. Other decoder arrangements may be provided using three or more inputs from the registers to control the number and repetition rate of the pulse sequence.

Different pulse sequences can be obtained on command by coupling both the decoders of FIGURES 2 and 4 to the register stages. An additional command lines S8 is coupled to all the gates of the decoder 34, and another command line 82/3 is coupled to all the gates of the decoder 34. In operation when an eight pulse sequence is desired the command line S8 is activated by any suit able means to enable the decoder 34 gates. When a three pulse sequence is desired the 82/3 command line is activated enabling the decoder 34 gates. In certain instances both command line S8 and 82/3 can be activated to produce both sets of pulse sequences.

FIGURE 5 is a schematic diagram of a flip-flop suitable for use in register stage. The flip-flop of stage C0, for example, comprises a pair of transistor NAND gates 40 and 42 of known type. The transistors are of PNP type and have their respective collector-base electrodes crosscoupled to each other via a coupling diode and a base input resistor. A speed-up capacitor is connected in parallel with the base resistor. The emitter electrodes are connected to a positive bias indicated as +6.5 volts. The collector electrodes are connected by resistors to a negative supply potential indicated as 19.5 volts. The collectors are also clamped close to ground potential by clamp diodes. Bias potentials of +13 and -l9.5 volts are resistor coupled across the base input resistors. The trigger input (T) is coupled by way of a pulse steering network 43 to the bases of the transistors. Each branch of the network 4-3 includes a capacitor and a diode D1 or D2. Separate resistors connected to the set and reset inputs are used to forward bias one of the steering diodes. A common reset terminal 44 may be connected by way of diode 46 to the base input resistor of the gate 40. The C0 and C5 output terminals are connected, respectively, to the collectors of the transistors 42 and 40.

In operation, the collectors potential of a NAND gate is low, i.e., close to ground potential, when any one of its inputs is high, and is high, i.e., close to 6.5 volts, when all its inputs are low. The flip-flop is arranged so that one transistor is conducting, producing a high output and the other is nonconducting, producing a low output. In the set state, the transistor 40 is conducting, hence the C0 output is high and the C0 output is low. The high CE output is coupled as an enabling input to the steering diode D1 of the register stages C2 and C1. In the reset state the transistor 42 is conducting, hence the C0 output is high and the C6 output is low. The high Ctl output is applied as an enabling input to the steering diode D2 of the register stages C1 and C2. A positive polarity trigged pulse applied to trigger input (T) is coupled via the forward biased steering diode to the base of the connected transistor turning this transistor to the nonconducting condition, if it is not already there.

A positive reset pulse applied to common reset input 44 is passed by diode 46 to change the transistor gate 40 to the nonconducting condition, if it is not already nonconducting, thereby resetting the flip-flop.

What is claimed is: 1. A pulse generator comprising,

means including switch means responsive to outputs of certain others of said gates for applying set in- 4. A pulse generator comprising, first and second flip-flop registers each having m flipflops, the flip-flops of each register being connected in an a first register having a plurality of flip-flops connected ordered sequence with the 'both outputs of the lowin cascade, est order flip-flop of a first of said registers being a second register comprising a plurality of flip-flops applied as respective inputs to the lowest order flipconnected in cascade, flop of the second of said registers, each of said flip-flops ihaving set and reset inputs and an oscillator producing output signals,

corresponding outputs, and a trigger input for setting said oscillator signals being applied directly to said first the flip-flop to a state determined by the set and register flip-flops and said oscillator signals being inreset inputs, said cascade connection of each of said verted and applied to said second register flip-flops, first and said second register including circuit means and connecting said set and reset inputs of said flip-flops a decoder comprising a plurality of n gates, where n to respective outputs of preceding ones of said fiipis different from 2m, flops within each of said first and said second regeach said gate having one input connected to an outister put of said first register and another input connected an oscillator, to an output of said second register, means for applying one phase of oscillator pulses to successive ones of said gates being activated and dethe trigger inputs of said first register flip-flops, 2O activated in synchronism with said oscillator signals. means for applying the other phase oscillator pulses 5. A pulse generator as recited in claim 4 including, to the trigger inputs of said second register flip-flops, means for applying said input signals to the lowest said other oscillator pulses being 180 out of phase order flip-flop of said first register, and with respect to said one phase pulses, and means responsive to said first and second outputs for a decoder comprising a plurality of gates, a different providing reset inputs to said lowest order flip-flop one for each output pulse to be produced, of said first register. each of said gates having inputs connected to outputs 6. A pulse generator as recited in claim 4 where n is of certain flip-flops of both of said registers, greater than 2m. said gates producing output pulses which have a dif- 7. A pulse generator as recited in claim 4 where n is ferent repetition rate from that of said oscillator. less than 2m. 2. A pulse generator as recited in claim 1, including, A Pulse generator as recited in Claim 5, including, means for applying said inputs to the lowest order further means responsive to certain other of said gate flip-flop of said first register to initiate a pulse sequence, o tputs for applying an additional start input tosaid and lowest order flip-flop of said first register to initiate means for applying at a later time reset inputs intosaid an th r pulse Sequence.

lowest order first register flip-flops for terminating id pulse Sequence References Cited by the Examiner 3. A pulse generator as recited in claim 1, including, UNITED STATES PATENTS means for applying said inputs to said lowest order gig-152p of said first register to initiate a pulse sefi i ::::i: i 2 means responsive to outputs of certain of said gates to g i 32848 X aoletti et a1 32872 X P reset inputs 9 9 of 3,162,816 12/1964 Rakoczietal 32s 92 311g first register for terminating said pulse sequence, 3,168,700 2/1965 Gesek et a1 328 X 3,212,010 10/1965 Podlesny 328-63 ARTHUR GAUSS, Primary Examiner.

puts to said lowest order flip-flop of said first register B. P. DAVIS, Assistant Examiner.

to initiate a new pulse sequence. 

1. A PULSE GENERATOR COMPRISING, A FIRST REGISTER HAVING A PLURALITY OF FLIP-FLOPS CONNECTED IN CASCADE, A SECOND REGISTER COMPRISING A PLURALITY OF FLIP-FLOPS CONNECTED IN CASCADE, EACH OF SAID FLIP-FLOPS HAVING SET AND RESET INPUTS AND CORRESPONDING OUTPUTS, AND A TRIGGER INPUT FOR SETTING THE FLIP-FLOP TO A STATE DETERMINED BY THE SET AND RESET INPUTS, SAID CASCADE CONNECTION OF EACH OF SAID FIRST AND SAID SECOND REGISTER INCLUDING CIRCUIT MEANS CONNECTING SAID SET AND RESET INPUTS OF SAID FLIP-FLOPS TO RESPECTIVE OUTPUTS OF PRECEDING ONED OF SAID FLIPFLOPS WITHIN EACH OF SAID FIRST AND SAID SECOND REGISTER AN OSCILLATOR, MEANS FOR APPLYING ONE PHASE OF OSCILLATOR PULSES TO THE TRIGGER INPUTS OF SAID FIRST REGISTER FLIP-FLOPS, MEANS FOR APPLYING THE OTHER PHASE OSCILLATOR PULSES TO THE TRIGGER INPUTS OF SAID SECOND REGISTER FLIP-FLOPS, SAID OTHER OSCILLATOR PULSES BEING 180* OUT OF PHASE WITH RESPECT TO SAID ONE PHASE PULSES, AND A DECODER COMPRISING A PLURALITY OF GATES, A DIFFERENT ONE FOR EACH OUTPUTS PULSE TO BE PRODUCED, EACH OF SAID GATES HAVING INPUTS CONNECTED TO OUTPUTS OF CERTAIN FLIP-FLOPS OF BOTH OF SAID REGISTER, SAID GATES PRODUCING OUTPUT PULSES WHICH HAVE A DIFFERENT REPETITION RATE FROM THAT OF SAID OSCILLATOR. 